Magnet core

ABSTRACT

A magnet core has a linear B-H loop, a high modulability with alternating current and direct current, a relative permeability of more than 500 but less than 15,000, and a saturation magnetostriction lambdas of less than 15 ppm, and is made of a ferromagnetic alloy, at least 50 percent of which consist of fine crystalline parts having an average particle size of 100 nm or less (nanocrystalline alloy) and which is characterized by formula FeaCobNicCudMeSifBgXh, wherein M represents at least one of the elements V, Nb, Ta, Ti, Mo, W, Zr, Cr, Mn, and Hf, a, b, c, d, e, f, g are indicated in atomic percent, X represents the elements P, Ge, C and commercially available impurities, and a, b, c, d, e, f, g, h satisfy the following conditions: 0&lt;=b&lt;=40; 2&lt;c&lt;20; 0.5&lt;=d&lt;=2; 1&lt;=e&lt;=6; 6.5&lt;=f&lt;=18; 5&lt;=g&lt;=14; h&lt;5 atomic percent; 5&lt;=b+c&lt;=45, and a+b+c+d+e+f=100.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of co-pending InternationalApplication No. PCT/EP2004/003485 filed Apr. 1, 2004, which designatesthe United States of America, and claims priority to German applicationnumber 103 15 061.7-11 filed Apr. 2, 2003, the contents of which arehereby incorporated by reference in their entirety.

TECHNICAL FIELD

The invention concerns a magnet core with high modulability foralternating current and direct current components, a method forproduction of such a magnetic core and applications of such a magnetcore especially in current transformers and current-compensatedinductors, as well as alloys and bands for production of such a magnetcore.

BACKGROUND

High modulability for ac and dc components is required for numerousapplications of magnet cores in which, depending on the case, specificmodulability for ac and dc is necessary. Applications of magnet coreswith high modulability for ac and dc components are present, forexample, in current transformers and current-compensated inductors.

Current-compensated noise suppression inductors are described in DE-A 3526 047 and DE 195 48 530 A1. They have two windings for one-phaseapplication and three or more windings for multiphase applications. Thewindings of noise suppression inductors are connected so that themagnetic fluxes that are induced by the operating current rise mutually,whereas interference currents that flow with the same phase through thetwo windings result in magnetization of the soft magnetic core. Becauseof this the current-compensated noise suppression inductor produced actsas a very small inductive resistance with reference to the operatingcurrents, whereas interference currents, which come from connectedequipment, for example, and are closed via the ground, encounter veryhigh inductance.

The core of the known current-compensated noise suppression inductors isproduced from amorphous or amount of crystalline alloys, preferably bandmaterial. The inductance of the inductor then depends essentially on therelative permeability of the soft magnetic material of the magnet core,in addition to the number of windings and the core cross section.

Current transformers with the magnet cores mentioned in the introductioncan be used in watt meters, as described for example in WO 00/30131.Watt meters are used, for example, to record power consumption ofelectrical equipment and installations in industry and the household.The oldest useful principle is the Ferraris meter. The Ferraris meter isbased on power metering via the rotation of a disk connected to amechanical meter, which is driven by the current- orvoltage-proportional fields of corresponding field coils. For expansionof the functional capabilities of watt meters, like multiple rateoperation or remote reading, electronic watt meters are used in whichcurrent and voltage recording occurs via current and voltage converters.The output signals of these converters are digitized, multiplied,integrated and stored; the result is an electrical quantity that isavailable for remote reading.

One of the possible technical variants of such a current converter isthe current transformer according to the induction principle. FIG. 1shows a substitution circuit where this type of current transformer andthe ranges of the technical data can occur in different applications. Acurrent transformer 1 is shown here. The primary winding 2, whichcarries the current I_(prim) to be measured and a secondary winding 3,which carries the secondary current I_(sec) are situated on a magnetcore constructed from a soft magnetic material. This current I_(sec) isautomatically adjusted so that the primary and secondary ampere turns inthe ideal case are the same size and oppositely directed. The trend ofthe magnetic fields in such a current transformer shown in FIG. 2, inwhich the losses in the magnet core are not considered because of theirgenerally low value. The current in the secondary winding 3 is then setaccording to the law of induction so that it attempts to prevent thecause of its formation, namely the time change of the magnetic flux inmagnet core 4.

In the ideal current transformer the secondary current, multiplied bythe ratio of number of windings is therefore negatively equal to theprimary current, which is explained by equation (1):

$\begin{matrix}{I_{\sec}^{ideal} = {- {I_{prim}\left( \frac{N_{prim}}{N_{\sec}} \right)}}} & (1)\end{matrix}$

This ideal case is never reached because of losses in the loadresistance 5, in copper resistance 6 of the secondary winding and in themagnet core 4.

In real current transformers the secondary current therefore has anamplitude error and a phase error relative to the above idealization,which is described by equation (2):

$\begin{matrix}{{{{Amplitude}\mspace{14mu} {error}\text{:}\mspace{14mu} {F(I)}} = \frac{I_{\sec}^{real} - I_{\sec}^{ideal}}{I_{\sec}^{ideal}}};{{{Phase}\mspace{14mu} {error}\text{:}\mspace{14mu} {\phi (I)}} = {{\phi \left( I_{\sec}^{real} \right)} - {\phi \left( {- I_{prim}} \right)}}}} & (2)\end{matrix}$

The output signals of such a current transformer are digitized andfurther processed in the electronics of the watt meter.

The electronic watt meters used for power metering in industrialapplications operate indirectly because of the often very high (»100 A),i.e., special primary current transformers are connected in front of thecurrent input so that only pure bipolar, zero-symmetric alternatingcurrents (typically 1 . . . 6 A_(eff)) need be measured in the counteritself. For this purpose current transformers are used constructed frommagnet cores of highly-permeable materials, for example nickel-ironalloys containing about 80 wt % nickel and known under the name“Permalloy”. These have in principle a very low phase error φ to achievelow measurement errors, for which reason they are also equipped withvery many (typically more than 1000) secondary windings.

For use in household meters, which can also be used in small industrialinstallations, these are not suitable, since with the usual directconnection without primary current transformers connected in front tocurrent intensities can generally be 100 A and more and because of thisthe above described current transformers will be saturated. In addition,these currents can contain non-zero-symmetric do fractions that aregenerated by semiconductor circuits used in modern electrical equipment(for example, rectifier or phase control circuits) and which saturatecurrent transformers with highly permeable magnet cores magnetically andtherefore distort the power metering.

The international standards that apply for this of the IEC 62053stipulate that an electronic watt meter must be able to measure amaximum amplitude of a unipolar half-wave rectified sinusoidal currentwith a maximum additional error of 3 or 6% to comply with the accuracyclasses 1 and 2% for a stipulated maximum measurable effective valueI_(max) of a bipolar zero-symmetric sinusoidal current, the numericalvalue of which is equal to the maximum effective value. In addition tothese standards there are regional and national provisions that permitas sufficiently precisely defined behavior power recording even with alow amplitude limit value of the unipolar current.

To form such current, current converters are known which operates on thebasis of open magnetic circuits or low-permeability magnetic circuitssheared with mechanically introduced air gaps. An example of such acurrent converter is a current transformer in which a ferrite-shell coreprovided with an air gap (sheared) is used as magnet core. This hassatisfactory linearity as a function of primary current, but because ofthe relatively low saturation induction of ferrite a comparatively largevolume magnetic core is required in order to achieve a high maximummeasurable primary current with high linearity over the entire currentrange in the current transformers. These current transformers also havehigh sensitivity to external foreign fields so that fielding measuresmust also be taken, which are material- and installation-intensive andtherefore not very favorable in terms of cost. In addition, the magneticvalues are generally strongly temperature dependent in ferrites.

Current converters are also known that operate on the basis of iron-freeair coils. This principle is known as the so-called Rogowski principle.The effect of the properties of a soft magnetic material on measurementaccuracy drops out here. Owing to the magnetically open design of suchcurrent converters, they must be equipped with particularly demandingshields against external fields, which is also cost-intensive because ofthe material and installation expenditure.

A technically high-value possibility for implementation is the use ofcurrent transformers with relatively low permeability (μ=1400-3000)magnet cores from fast-solidified amorphous soft magnetic materials. Thevery good constancy of this permeability during changes in the levelcontrol guarantees very high linearity of the phase error over theentire current range to be transmitted. Because of the low permeabilityvalue saturation with the do fractions is avoided within calculablelimits; on the other hand, it leads to the occurrence of a comparativelyhigh phase error between the primary and secondary current, which mustbe compensated in watt meters by a corresponding electronic circuit orsoftware. In previously known variants of electronic watt meters acompensation range of typically 0.5-5° is present, in which compensationof higher values of this range, however, requires increasing demandswith reference to signal processing semiconductor circuits and memories,which increases the equipment cost. A serious problem from thestandpoint of manufacturers competing on the market for watt meters arethe costs for the magnetic materials to be used, since the previouslyused alloys contain about 80 atom % Co, which leads to a comparativelyhigh material price.

SUMMARY

It is the task of the invention to improve a magnet core that hasmodulability for ac and dc components in its application-relatedproperties. Another task of the invention is to design the magnetic corewith respect to its properties so that it is suitable for differentapplications, as well as applications for such a magnet core. Anothertask of the present invention is to provide a particular cost-effectivemagnet core. A final task of the invention is to provide a productionmethod for such magnet cores.

The object can be achieved by a magnet core with a linear B-H loop and ahigh modulability in alternating current and direct current, comprisinga relative permeability μ that is greater than 500 and less than 15,000,having a saturation magnetostriction λ_(s) whose amount is less than 15ppm and consisting of a ferromagnetic alloy in which at least 50% of thealloy consists of fine crystalline particles with an average particlesize of 100 nm or less (nanocrystalline alloy) and is characterized bythe formula Fe_(a)Co_(b)Ni_(c)Cu_(d)M_(e)Si_(f)B_(g)X_(h) in which M isat least one of the elements from the group consisting of V, Nb, Ta, Ti,Mo, W, Zr, Cr, Mn and Hf, a, b, c, d, e, f, g are stated in atom %, Xdenotes the elements P, Ge, C as well as commercial dopants and a, b, c,d, e, f, g, h satisfy the following conditions:

0≤b≤40;2<c<20;0.5≤d≤2;1≤e≤6;6.5≤f≤18;5≤g≤14;h<5 atom %with 5≤b+c≤45, in which a+b+c+d+e+f=100.

Furthermore, a, b, c, d, e, f, g, h may satisfy the followingconditions:

0≤b≤20;2<c<15;0.5≤d≤2;1≤e≤6;6.5≤f≤18;5≤g≤14;h<5 atom %with 5≤b+c≤30, in which a+b+c+d+e+f=100.

Moreover, a, b, c, d, e, f, g, h may satisfy the following conditions:

0≤b≤10;2<c<15;0.5≤d≤2;1≤e≤6;6.5≤f≤18;5≤g≤14;h<5 atom %with 5≤b+c≤20, in which a+b+c+d+e+f=100.

Also, a, b, c, d, e, f, g, h may satisfy the following conditions:

0.7≤d≤1.5;2≤e≤4;8≤f≤16;6≤g≤12; withh<2.

The Co content can be less than or equal to the Ni content. The magnetcore can be in the form of an annular band core (toroidal core) woundfrom a band with a thickness of less than 50 μm. The amount of thecoercitivity field intensity H_(c) can be less than 1 A/cm. Theremanence ratio can be less than 0.1. The magnet core may have arelative permeability μ greater than 1000 and less than 10,000,particularly a relative permeability μ greater than 1500 and less than6000. The saturation magnetostriction λ_(s) can be less than 10 ppm. Atleast 50% of the alloy can be accompanied by fine crystalline particleswith an average particle size of 50 nm or less. The magnet core can beconfigured as a closed toroidal core, oval core or rectangular corewithout air gap. The magnet core can be fixed in a trough. For fixationof the core a soft elastic reaction adhesive and/or a soft plasticnonreactive paste can be prescribed.

The object can also be achieved by method for production of such amagnet core, wherein the method comprises the step of performing a heattreatment in a magnetic transverse field of the magnet core.

A heat treatment can also be also performed in a magnetic longitudinalfield. A heat treatment can also be performed in the transverse fieldbefore a heat treatment in a longitudinal field. Alternatively, a heattreatment may be performed in the transverse field after heat treatmentin a longitudinal field.

The object can further be achieved by a current transformer foralternating power with such a magnet core, wherein the currenttransformer, in addition to the magnetic core as transformer core, has aprimary winding and at least one secondary winding in which thesecondary winding is low-resistance terminated by a load resistanceand/or measurement electronics.

The current transformer may have a phase error of a maximum 7.5° C. in acircuit with a load resistance and/or measurement electronics accordingto a respective specification and dimension. The current transformer mayalso have a phase error of a maximum 5° C. in a circuit with a loadresistance and/or measurement electronics according to a respectivespecification and dimension.

The object can further be achieved by a current-compensated inductorwith the above described magnet core wherein the inductor has at leasttwo windings in addition to the magnet core.

The inductor may have an insertion attenuation of at least 20 dB in thefrequency range from 150 kHz to 1 MHz even during flow of a dischargecurrent of at least 10% of the nominal current. The inductor may alsohave an insertion attenuation of at least 20 dB in the frequency rangefrom 150 kHz to 1 MHz even during flow of a discharge current of atleast 20% of the nominal current.

In comparison with the prior art a current transformer is significantlyimproved with a magnet core according to the invention in its properties(for example temperature trend, phase error, maximum primary current,maximum unipolar primary current as well as cost) relative to knowncurrent transformers (for example with ferrite cores). The magnet corecan also be designed without an air gap enclosed. In addition to highmodulability for ac and dc components, it has excellent suitable highlinearity of current formation especially for current meter applicationsover a wide current range at high immunity to external foreign magneticfields without initial shielding measures. It has therefore beendemonstrated that the magnetic cores according to the invention areparticularly suitable for current transformers and current-compensatedinductors. However, they can also be advantageously used in any otherapplications.

Because of a simple design of the current transformers andcurrent-compensated inductors possible by the special properties of themagnet core according to the invention with low core masses from alloysthat also contain no or only limited amounts of the expensive elementCo, as well as with winding with relatively low number of turns, it canalso be produced very cheaply and is therefore particularly suitable forthe aforementioned applications. The temperature dependence of thementioned properties is also as low as possible.

In laying out a current transformer according to the invention for astipulated maximum primary current it was therefore assumed that thiscurrent is proportional to the material-specific saturation induction,the core cross section and inversely proportional to the sum of thevalues for the load resistance and the resistance of the secondarywinding. The core size (volume) is the product of core cross section andaverage magnetic path length. The core mass is obtained by multiplyingby the material density. At the same time the maximum unipolar currentamplitude is proportional to the material-specific saturation inductionand to the average magnetic path length of the core and inverselyproportional to the permeability of the material.

A minimal phase error was then achieved, which roughly up to a value ofthe phase error of about ≤8° is proportional to the aforementionedresistance sum and inversely proportional to permeability. In addition,the greatest possible saturation induction was sought. The amorphousmaterials with about 80 atom % Co have values for saturation inductionof 0.8-1 T. An increase would permit a reduction of the magnet core withthe same maximum current or an increase in maximum current at the samecore size.

It is initially assumed that the core size (core volume) remainsconstant. The quantities also generally determined by the meterdesigner, like number of secondary windings as well as load resistanceshould not change either. The current transformer during an increase insaturation induction from 0.9 T to 1.2 T, as a nanocrystalline materialwith 10 atom % Ni has, for example, would therefore be able to form a33% higher primary current. In addition, such a design with equivalentmaximum unipolar current amplitude with increased saturation inductionand equivalent core size would permit higher permeability, for examplean increase from 1500-3000 in an amorphous material with about 80 atom %Co to 2000-4000 for a nanocrystalline material with 10 atom % Ni. Thisagain leads to a roughly 25% lower phase error, which significantlyreduces the compensation expense in the watt meter. If the possibilityfor reducing the core cross section by 25% is then used for equivalentmaximum primary current and the size ratios are correspondingly adjustedfor the purpose of reducing the resistance of the secondary winding, itis possible to half the phase error of 5° to 2.5 with the same loadresistance.

The costs for the core material in this case during use ofnanocrystalline material with 10 atom % Ni could be reduced to about 30%of the material costs and a core made of amorphous material with about80 atom % Co.

A preferred variant of a magnet core according to the invention suitablein particular for use in a current transformer proposes that the magnetcore consist of a round band of ferromagnetic alloy in which at least50% of the alloy is occupied by five crystalline particles with anaverage particle size of 100 nm or less, preferably 50 nm or less(nanocrystalline alloy), having permeability greater than the housing,preferably 1500 and less than 10,000, preferably 6000, which is setperpendicular to the direction of magnetization by tempering in amagnetic field. The saturation induction is then greater than or equalto 1 Tesla.

Further preferred variants also have a saturation magnetostrictionλ_(s)<15 ppm (preferably <10 ppm). Such properties can ordinarily beachieved either based only on expensive Co-based alloys, whereas innanocrystalline Fe-based alloys the permeability range in common alloysis greater than 10,000. The alloy for a magnet core according to theinvention has a composition described essentially with the formula

Fe_(a)Co_(b)Ni_(c)Cu_(d)M_(e)Si_(f)B_(g)X_(h)

in which M is at least one of the elements V, Nb, Ta, Ti, Mo, W, Zr, Cr,Mn and Hf, a, b, c, d, e, f, g are stated in atom %, X denotes theelements P, Ge, C as well as commercial dopants and in which a, b, c, d,e, f, g, h satisfy the following conditions:

0≤b≤40;

2<c<20;

0.5≤d≤2;

1≤e≤6;

6.5≤f≤18;

5≤g≤14;

h<5 atom %

with 5≤b+c≤45, in which a+b+c+d+e+f=100.

Magnet cores with an alloy composition a, b, c, d, e, f, g, h thatsatisfy the following conditions are preferred:

0≤b≤20;

2<c<15;

0.5≤d≤2;

1≤e≤6;

6.5≤f≤18;

5≤g≤14;

h<5 atom %

with 5≤b+c≤30, in which a+b+c+d+e+f=100.

Magnet cores with an alloy composition a, b, c, d, e, f, g, h thatsatisfy the following conditions are particularly preferred:

0≤b≤10;

2<c<15;

0.5≤d≤2;

1≤e≤6;

6.5≤f≤18;

5≤g≤14;

h<5 atom %

with 5≤b+c≤20, in which a+b+c+d+e+f=100.

Excellent results are provided by magnet cores whose alloy compositionssatisfy the following conditions:

0.7≤d≤1.5;

2≤e≤4;

8≤f≤16;

6≤g≤12;

h<2 atom %

with 5≤b+c≤20, in which a+b+c+d+e+f=100. Preferably the variants have aCo content that is less than the Ni content.

It has been shown that such a magnet core the dependence of permeabilityon magnetization is very small. The hysteresis loop of the magnet coreis therefore very narrow and linear. This requires the smallest possibleratio of remanence induction to saturation induction of less than 30% ifpossible, preferably 20% and low coercivity field intensities of lessthan 1 A/cm if possible, better 0.2 A/cm. This leads to high constancyof the permeability values. The nonlinearity of permeability Δμ/μ<15%(better less than 10%) in which Δμ represents the largest value for thedifference between minimal and maximal value of the permeability overthe entire measurable magnetization range up to about 5% below thesaturation induction of 1.2 Tesla and μ is the average permeability inthis magnetization range.

A current transformer with a magnet core according to the invention has,in addition to the magnet core, at least primary winding and onesecondary winding, with which a load resistance is connected in paralleland which closes off the secondary circuit with low resistance. Sincethe permeability of the magnet core in the mentioned range isessentially independent of magnetization, the absolute phase error andabsolute amplitude error of this current converter with such a magneticcore are then almost constant over a wide primary current range. Theabsolute amplitude error can be smaller than 1%. The absolute phaseerror can be less than 5°. Because of the good linearity the absolutevalues of the phase and amplitude errors can be easily compensated bythe electronics or software of the watt meter equipped with it, whichleads to high measurement accuracy for electrical power.

Because of its narrow crystalline structure the magnet core hassurprisingly high aging resistance, which permits an upper applicationtemperature limit for the magnet core above 120° C., special cases evenaround 150° C. Precisely because of this the current converter with amagnet core is suitable for use well above room temperature.

Properties of the magnet core are weakly temperature dependent, in whichthis dependence again is largely linear. The temperature coefficient ofpermeability should then have an absolute value much less than 0.5%/K,preferably less than 0.2%/K.

The invention is also based on the finding that with the alloy of thedescribed composition by appropriate heat treatment a magnet core withthe described properties can be produced. Very many parameters must beadjusted to each other so that the magnet core has the describedproperties.

Because of the nanocrystalline two-phase structure generated during heattreatment with simultaneously high saturation induction and high thermalstability, the underlying prerequisites for good soft magneticproperties are met. The core is preferably produced from bands, which inturn are produced from the alloy according to the invention.

BRIEF DESCRIPTION OF THE DRAWINGS

The invention is further explained below by means of the practicalexamples depicted in the figures of the drawing. In the drawing:

FIG. 1 shows a replacement circuit for a known current converter and theranges of the different technical data that can occur in an operation,

FIG. 2 shows the trend of the magnetic fields in a current converteraccording to FIG. 1,

FIG. 3 shows the trend of the amplitude error (in %) and the phase error(in °) as a function of primary current (in A) for a nominal primarycurrent I_(primN) of 640 Å,

FIG. 4 shows the trend of the amplitude error (in %) and the phase error(in °) as a function of primary current (in A) for a nominal primarycurrent I_(primN) of 400 Å and

FIG. 5 shows the hysteresis loop for a preferred alloy according to theinvention.

DETAILED DESCRIPTION

The area of application “current transformers with dc tolerance forelectric watt meters” is treated as an example below. It was found inthe pertinent investigations that, in the long known conventionalcurrent transformers with high-permeability cores, satisfaction of therequirements of the standard series IEC 62053 for dc tolerance is notpossible. These standards, which apply for the requirements ofelectronic household meters with direct connection, require that even inthe presence of half-wave-rectified (i.e., purely unipolar) sinusoidalcurrents power recording must be possible.

Conventional current transformers fail here because the highpermeability cores are very quickly saturated by the unipolar flux thatbuilds up. With diminishing permeability of the core material the timeconstant of the flux decline also drops with inductance so that thesolution to the problem was sought in the use of more low-permeableamorphous alloys. However, a shortcoming here is the comparatively highprice, which is mostly caused by the amorphous band of about 80% Co.

The starting point for the considerations is therefore defined inalternative very low-permeable (μ preferably about 1500-6000) alloyvariants suitable for replacing the amorphous low-permeability Co-basedband with significant cost advantages.

Clarification of the question whether the attainable linearityapproaches that of the excellent Co-based bands in this respect so thatthe requirements on accuracy of power measurement can be met is alsoimportant here. It can be accepted with some certain that the highersaturation induction can be transferred to the corresponding applicationon the way to optimization. A requirement is perfect functionalityaccording to IEC 62053, which previously had a significant technicaladvantage relative to the use of cheaper ferrite cores.

Initially bands were investigated that are varied in Si content and Nbcontent. The experimental program included two cores each of eachvariant with two different temperatures in the transverse field heattreatment and three alloy compositions in the context of randomexperiments in alloy variation bands were cast from the experimentalalloys with a width of 6.2 mm and processed to annular band cores. Thesewere treated to achieve the flattest possible hysteresis loop in thetransverse field at different temperatures. Initially the achievedaverage permeabilities μ_(av) and other base parameters were determined(see Table 1).

TABLE 1 Alloys with V and Ni additives. Core T_(QF) B_(max) H_(c) H_(a)μ λ₂ No. Fe Ni Cu Nb V Si B (° C.) (T) B_(r)/B_(m) (mA/cm) (A/cm) (av)(ppm) 1A Rem 10 1 3 0 15.9 6.6 540 1.12 0.008 13 1.75 5.083 4.4 1B Rem10 1 3 0 15.9 6.6 470 1.13 0.009 15 2.01 4.463 2.8 2A Rem 10 1 3 0 12.58 540 1.19 0.008 19 2.95 3.198 7.7 2B Rem 10 1 3 0 12.5 8 570 1.20 0.01135 3.49 2.735 6.7 3A Rem 10 1 1.5 1.5 12.5 8 540 1.20 0.016 59 3.712.578 6.5 3B Rem 10 1 1.5 1.5 12.5 8 570 1.20 0.057 216 3.94 2.425 5.8Rem = remainder

At the beginning of the study all cores were inserted stress-free introughs without filler, which were then suitably wound for the linearitymeasurements, in which the values at 25° C. were initially considered.The results are summarized in Table 2.

TABLE 2 Alloys with V and Ni additives and unfixed linearity (voltagestress-free in the trough). Core T_(QF) Δμ/μ_(av) No. Fe Ni Cu Nb V Si B(° C.) μ_(av) (%) 1A-1 Remainder 10 1 3 0 15.9 6.6 540 5598 6.13 1A-2Remainder 10 1 3 0 15.9 6.6 540 5605 6.24 1B-1 Remainder 10 1 3 0 15.96.6 570 4919 6.97 1B-2 Remainder 10 1 3 0 15.9 6.6 570 4888 6.79 2A-1Remainder 10 1 3 0 12.5 8 540 3549 5.49 2A-2 Remainder 10 1 3 0 12.5 8540 3523 5.52 2B-1 Remainder 10 1 3 0 12.5 8 570 3033 4.12 2B-2Remainder 10 1 3 0 12.5 570 2981 3.48 3A-1 Remainder 10 1 1.5 1.5 12.5 8540 2724 5.88 3A-2 Remainder 10 1 1.5 1.5 12.5 8 540 2714 5.46 3B-1Remainder 10 1 1.5 1.5 12.5 8 570 2282 12.5 3B-2 Remainder 10 1 1.5 1.512.5 8 570 2300 12.5

For a better overview the linearity of the current trends is expressedby the dimensions Δμ/μ_(av), in which the last two data points onreaching saturation were not included in the average value. The magnetcores mostly show a linearity that is suitable to ensure the requiredprecision of power measurement over a wide current range during use ofthe cores for current transformers in electronic watt meters. Anexception is variant 3B in which a relatively high value with 12.5% wasachieved, which presumably was caused by overtempering in the transversefield.

To determine the applications of the related fixation effect a core ofeach variant was either coated with an insulating plastic layer orinserted into an adapted plastic trough with soft elastic adhesive andwound/measured again. Significantly different pictures for linearitybehavior of the cores were obtained, which is apparent from the twofollowing Tables 3 and 4.

TABLE 3 Linearity fixed close to production (plastic layer). Core Δμ/type/ T_(QF) μ_(av) no. Fe Ni Cu Nb V Si B (° C.) μ_(av) (%) 1A-1Remainder 10 1 3 0 15.9 6.6 540 10,170 151 1B-1 Remainder 10 1 3 0 15.96.6 570 8403 138 2A-1 Remainder 10 1 3 0 12.5 8 540 6555 161 2B-1Remainder 10 1 3 0 12.5 8 570 4881 129 3A-1 Remainder 10 1 1.5 1.5 12.58 540 3696 82.9 3B-1 Remainder 10 1 1.5 1.5 12.5 8 570 2262 35.1

TABLE 4 Linearity fixed close to production (plastic trough withself-elastic adhesive). Core type/ T_(QF) Δμ/μ_(av) no. Fe Ni Cu Nb V SiB (° C.) μ_(av) (%) 1A-1 Remainder 10 1 3 0 15.9 6.6 540 5716 13.2 1B-1Remainder 10 1 3 0 15.9 6.6 570 4947 5.15 2A-1 Remainder 10 1 3 0 12.5 8540 3587 5.46 2B-1 Remainder 10 1 3 0 12.5 8 570 3033 3.06 3A-1Remainder 10 1 1.5 1.5 12.5 8 540 2699 6.74 3B-1 Remainder 10 1 1.5 1.512.5 8 570 2305 12.7

Table 3 shows a very distinct effect of the plastic layer of linearityof the characteristic via the magnetostriction caused by the Ni additionthe material reacts so strongly to the shrinkage stress of the layersolidifying at about 120° C. and contracting during cooling that theresulting linearities no longer appear to be useful for use in aprecision current transformer. The linearity deviations reach valuesthat lie by a factor of 9 to more than 50 above the values ofmagnetostriction-free amorphous Co-based alloys used for comparison.

A much more favorable behavior is caused by trough fixation. Here,during use of a soft elastic adhesive the nonlinearities only rise by amaximum of a factor of 2. In each case the variants 1B, 2A, 2B and 3Aappear to be useful at room temperature for use of high linear currenttransformers. For subsequent considerations concerning use over a broad(for example −40 to +70° C.) temperature range, the temperatureproperties of the complex permeability were also considered. Forexample, the trends for the core 2A-2 show a negative temperaturecoefficient of permeability that is almost linear between −40 and +85°C. and has a value of about −0.1%/K for core 2B-2. The value appliesboth for amplitude of the existing field of 4 mA/cm and for 15 mA/cm. Itwas found that a positive temperature coefficient for the currenttransformer is favorable to the extent that it behaves opposite theincreasing resistance of the copper wire at increasing temperature andtherefore reduces the phase error. During design of the currenttransformers, the resulting larger variation of errors with temperaturemust therefore be kept in mind. During use of the soft elastic adhesiveit was found that a temperature change both at high and low temperaturesleads to addition of linearity deviations of the converter errors.Tensile and compressive stresses occur here on the core, which aretransferred because of the elastic behavior of the hardened adhesivefrom the trough material. A significant reduction of this effect couldbe achieved by using as filler a soft plastic nonreactive paste insteadof a soft elastic reaction adhesive. Linearity values could therefore bekept almost constant within the temperature range from −40 to +85° C.

A distinct advantage of the nanocrystalline material is the variabilityof permeability, which curing use of trough fixation must also betransported with satisfactory linearity into application. Because of theexpanded useful level control range a de-tolerant current transformercan easily be tuned to an optimum of preloadability. To improvelinearities, the magnetostriction can also be reduced if the percentageof added nickel is reduced by 10% in order to arrive at permeabilitiesof 4000 or 6400.

FIGS. 3 and 4 show the trend of the amplitude error (in %) and the phaseerror (in °) as a function of primary current (in A) for differentnominal primary currents I_(primN) of 640 A (FIG. 3) and 400 A (FIG. 4).

FIG. 5 finally shows the hysteresis loop (magnetic flux B in T over thefield intensity H in A/cm) for an alloy with 65.2 atom % Fe, 12 atom %Ni, 0.8 atom % Cu, 2:5 atom % Nb, 11.5 atom % Si and 8 atom % B. Thisalloy is compared with other alloys according to the invention in Table5, in which QF stands for the transverse field treatment and LF forlongitudinal field treatment. The alloys marked with an * are comparisonalloys that do not belong to the invention.

Heat treatment in the transverse field (transverse field treatment QF)is always necessary, in which the permeability can be arbitrarilyadjusted with additional heat treatment in the longitudinal field(longitudinal field treatment LF) which can occur before or aftertransverse field treatment. This has the advantage that cores withdifferent properties can be produced from the same alloy and thereforedifferent classes of current transformers (current classes). Thecombination of temperature and duration of transverse field treatmentshould always have a stronger effect than temperature and duration oflongitudinal field treatment.

TABLE 5 B_(m) H_(c) TK λ_(s) Nr Fe Co Ni Cu Nb V Si B WB (T) B_(r)/B_(m)(A/cm) μ (%/° C.) (ppm)  1 75.5 0 1 3 12.5 8 0.5 h 550° C. QF 1.32 0.0060.005 10600 −0.25 4.4  2 70.5 5 1 3 12.5 8 0.5 h 550° C. QF 1.28 0.0010.008 5020 −0.18 —  3a 65.5 10 1 3 12.5 8 0.5 h 570° C. QF 1.23 0.0060.019 2630 −0.13 —  3b 65.5 10 1 3 12.5 8 0.5 h 550° C. QF 1.21 0.0010.005 2837 −0.17 —  3c 65.5 10 1 3 12.5 8 0.5 h 540° C. QF 1.19 0.0080.019 3200 −0.16 7.7  3d 65.5 10 1 3 12.5 8 0.5 h 550° C. LF + 1.210.001 0.015 6080 −0.05 — 3 h 500° C. QF  3e 65.5 10 1 3 12.5 8 0.5 h550° C. LF + 1.20 0.003 0.030 7140 −0.01 — 3 h 460° C. QF  3f 65.5 10 13 12.5 8 0.5 h 550° C. LF + 1.20 0.002 0.018 8360 0.03 — 3 h 423° C. QF 4 65.5 10 1 1.5 1.5 12.5 8 0.5 h 540° C. QF 1.20 0.016 0.059 2578 −0.166.5  5a 60.5 15 1 3 12.5 8 0.5 h 550° C. QF 1.12 0.005 0.026 1860 −0.12—  5b 60.5 15 1 3 12.5 8 0.5 h 550° C. LF + 1.12 0.036 0.073 4590 0.03 —3 h 500° C. QF  5c 60.5 15 1 3 12.5 8 0.5 h 550° C. LF + 1.12 0.0360.061 5420 −0.001 — 3 h 460° C. QF  5d 60.5 15 1 3 12.5 8 0.5 h 550° C.LF + 1.12 0.044 0.031 6490 0.02 — 3 h 423° C. QF  6 55.5 20 1 3 12.5 80.5 h 550° C. QF 0.18 0.140 1.14 1.75  7 64.5 10 1 3 14 7.5 0.5 h 550°C. QF 1.10 0.005 0.012 3520 −0.15 —  8 66 10 1 3 11 9 0.5 h 550° C. QF1.25 0.001 0.003 2617 −0.15 8.7  9a 63.5 10 1 3 15.9 6.6 0.5 h 550° C.QF 1.14 0.002 0.003 4307 −0.12 —  9b 63.5 10 1 3 15.9 6.6 0.5 h 540° C.QF 1.12 0.008 0.013 5080 −0.09 4.4 10 63.5 10 1 1.5 1.5 15.9 6.6 0.5 h540° C. QF 1.12 0.011 0.026 3400 −0.12 3.1 11 66.7 10 0.8 3 11.5 8 0.5 h550° C. QF 1.23 0.000 0.002 2610 −0.14 8.1 12 67 10 0.8 2.7 11.5 8 0.5 h550° C. QF 1.27 0.001 0.003 2610 −0.13 — 13 69.2 8 0.8 2.5 11.5 8 0.5 h550° C. QF 1.32 0.012 0.041 3090 −0.12 7.6 14 67.2 10 0.8 2.5 11.5 8 0.5h 550° C. QF 1.29 0.006 0.022 2650 −0.12 — 15 65.2 12 0.8 2.5 11.5 8 0.5h 550° C. QF 1.26 0.004 0.019 2230 −0.11 8.8 16 63.2 14 0.8 2.5 11.5 80.5 h 550° C. QF 1.16 0.110 0.620 1720 0.09 — 17 67.4 10 0.8 2.3 11.5 80.5 h 550° C. QF 1.30 0.016 0.063 2610 −0.09 — 18 67.6 10 0.8 2.1 11.5 80.5 h 550° C. QF 1.30 0.064 0.253 2600 0.04 — 19 66.8 10 0.8 2.9 11.5 80.5 h 550° C. QF 1.25 0.012 0.041 2787 −0.14 7.9 20 61.8 5 10 0.8 2.911.5 8 0.5 h 550° C. QF 1.25 0.008 0.039 2045 −0.13 10.7 21 56.8 10 100.8 2.9 11.5 8 0.5 h 550° C. QF 1.24 0.012 0.073 1627 −0.15 12.5 22 46.820 10 0.8 2.9 11.5 8 0.5 h 550° C. QF 1.22 0.015 0.127 1097 −0.16 20.523 36.8 30 10 0.8 2.9 11.5 8 0.5 h 550° C. QF 1.17 0.018 0.208 845 −0.1723.5 24 26.8 40 10 0.8 2.9 11.5 8 0.5 h 550° C. QF 1.03 0.040 0.519 582−0.46 22

The values listed in the above Table 5 mean:

-   1. QF=heat treatment in magnetic transverse field, LF=heat treatment    in magnetic transverse field.-   2. Bm was measured at a maximum field intensity of Hm=8 A/cm for    examples 1 to 21 and Hm=32 A/cm for examples 22 to 24.-   3. μ denotes the average permeability, defines the average slope of    the hysteresis curve.-   4. No. 1 and No. 6 are comparative examples NOT according to the    invention.

The numbering of the alloys from Table 5 differs from that in Tables1-4. The permeability values between Table 5 and the other tables cantherefore easily differ, since different experimental series areinvolved.

With the magnet cores according to the invention current transformerscan be produced in Which the maximum undistorted amplitude of ahalf-wave electrified sinusoidal primary current has a numerical valueat least 10%, better 20% of the effective value of the maximumundistorted bipolar sinusoidal primary current.

What is claimed is:
 1. A magnet core with a linear B-H loop and a highmodulability in alternating current and direct current, comprising arelative permeability μ that is greater than 500 and less than 15,000, asaturation magnetostriction λ_(s) whose amount is less than 15 ppm andconsisting of a ferromagnetic alloy in which at least 50% of the alloyconsists of fine crystalline particles with an average particle size of100 nm or less and is characterized by the formulaFe_(a)Co_(b)Ni_(c)Cu_(d)M_(e)Si_(f)B_(g)X_(h) in which M is at least oneof the elements from the group consisting of V, Nb, Ta, Ti, Mo, W, Zr,Cr, Mn and Hf, a, b, c, d, e, f, g are stated in atom %, X denoteselements P, Ge, C as well as commercial dopants and a, b, c, d, e, f, g,h satisfy the following conditions: 0≤b≤40; 2<c<20; 0.5≤d≤2; 1≤e≤6;6.5≤f≤18; 5≤g≤14; h<5 atom % with 5≤b+c≤45, in which a+b+c+d+e+f=100. 2.A magnet core according to claim 1, wherein a, b, c, d, e, f, g, hsatisfy the following conditions: 0≤b≤20; 2<c<15; 0.5≤d≤2; 1≤e≤6;6.5≤f≤18; 5≤g≤14; h<5 atom % with 5≤b+c≤30, in which a+b+c+d+e+f=100. 3.A magnet core according to claim 1, wherein a, b, c, d, e, f, g, hsatisfy the following conditions: 0≤b≤10; 2<c<15; 0.5≤d≤2; 1≤e≤6;6.5≤f≤18; 5≤g≤14; h<5 atom % with 5≤b+c≤20, in which a+b+c+d+e+f=100. 4.A magnet core according to claim 1, wherein a, b, c, d, e, f, g, hsatisfy the following conditions: 0.7≤d≤1.5; 2≤e≤4; 8≤f≤16; 6≤g≤12; withh<2.
 5. A magnet core according to claim 1, wherein a Co content is lessthan or equal to a Ni content.
 6. A magnet core according to claim 1,wherein the magnet core is in the form of an annular band core woundfrom a band with a thickness of less than 50 μm.
 7. A magnet coreaccording to claim 1, wherein the amount of a coercitivity fieldintensity H_(c) is less than 1 A/cm.
 8. A magnet core according to claim1, wherein a remanence ratio is less than 0.1.
 9. A magnet coreaccording to claim 1 having a relative permeability μ greater than 1000and less than 10,000.
 10. A magnet core according to claim 1 having arelative permeability μ greater than 1500 and less than
 6000. 11. Amagnet core according to claim 1, wherein a saturation magnetostrictionλ_(s) is less than 10 ppm.
 12. A magnet core according to claim 1,wherein at least 50% of the alloy is accompanied by fine crystallineparticles with an average particle size of 50 nm or less.
 13. A magnetcore according to claim 1, wherein the magnet core is configured as aclosed toroidal core, oval core or rectangular core without air gap. 14.A magnet core according to claim 1, wherein the magnet core is fixed ina trough.
 15. A magnet core according to claim 14, wherein for fixationof the core a soft elastic reaction adhesive and/or a soft plasticnonreactive paste is provided.
 16. A method for production of a magnetcore comprising a relative permeability μ that is greater than 500 andless than 15,000, a saturation magnetostriction λ_(s) whose amount isless than 15 ppm and consisting of a ferromagnetic alloy in which atleast 50% of the alloy consists of fine crystalline particles with anaverage particle size of 100 nm or less and is characterized by theformula Fe_(a)Co_(b)Ni_(c)Cu_(d)M_(e)Si_(f)B_(g)X_(h) in which M is atleast one of the elements from the group consisting of V, Nb, Ta, Ti,Mo, W, Zr, Cr, Mn and Hf, a, b, c, d, e, f, g are stated in atom %, Xdenotes the elements P, Ge, C as well as commercial dopants and a, b, c,d, e, f, g, h satisfy the following conditions: 0≤b≤40; 2<c<20; 0.5≤d≤2;1≤e≤6; 6.5≤f≤18; 5≤g≤14; h<5 atom % with 5≤b+c≤45, in whicha+b+c+d+e+f=100, the method comprising the step of performing a heattreatment in a magnetic transverse field of the magnet core.
 17. Amethod according to claim 16, wherein a heat treatment is also performedin a magnetic longitudinal field.
 18. A method according to claim 16,wherein a heat treatment is performed in the transverse field before aheat treatment in a longitudinal field.
 19. A method according to claim16, wherein a heat treatment is performed in the transverse field afterheat treatment in a longitudinal field.
 20. A current transformer foralternating power with a magnet core comprising a relative permeabilityμ that is greater than 500 and less than 15,000, a saturationmagnetostriction λ_(s) whose amount is less than 15 ppm and consistingof a ferromagnetic alloy in which at least 50% of the alloy consists offine crystalline particles with an average particle size of 100 nm orless and is characterized by the formulaFe_(a)Co_(b)Ni_(c)Cu_(d)M_(e)Si_(f)B_(g)X_(h) in which M is at least oneof the elements from the group consisting of V, Nb, Ta, Ti, Mo, W, Zr,Cr, Mn and Hf, a, b, c, d, e, f, g are stated in atom %, X denotes theelements P, Ge, C as well as commercial dopants and a, b, c, d, e, f, g,h satisfy the following conditions: 0≤b≤40; 2<c<20; 0.5≤d≤2; 1≤e≤6;6.5≤f≤18; 5≤g≤14; h<5 atom % with 5≤b+c≤45, in which a+b+c+d+e+f=100,wherein the current transformer, in addition to the magnetic core astransformer core, has a primary winding and at least one secondarywinding, wherein the secondary winding is low-resistance terminated by aload resistance and/or measurement electronics.
 21. A currenttransformer according to claim 20 having a phase error of a maximum 7.5°C. in a circuit with a load resistance and/or measurement electronicsaccording to a respective specification and dimension.
 22. A currenttransformer according to claim 21 having a phase error of a maximum 5°C. in a circuit with a load resistance and/or measurement electronicsaccording to a respective specification and dimension.
 23. Acurrent-compensated inductor with a magnet core according to claim 1,wherein the inductor has at least two windings in addition to the magnetcore.
 24. A current-compensated inductor according to claim 23, whereinthe inductor has an insertion attenuation of at least 20 dB in thefrequency range from 150 kHz to 1 MHz even during flow of a dischargecurrent of at least 10% of the nominal current.
 25. Acurrent-compensated inductor according to claim 24, wherein the inductorhas an insertion attenuation of at lest 20 dB in the frequency rangefrom 150 kHz to 1 MHz even during flow of a discharge current of atleast 20% of the nominal current.